Telegrapher's equations

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The telegrapher's equations (or just telegraph equations) are a pair of coupled, linear differential equations that describe the voltage and current on an electrical transmission line with distance and time. The equations come from Oliver Heaviside who in the 1880s developed the transmission line model, which is described in this article. The model demonstrates that the electromagnetic waves can be reflected on the wire, and that wave patterns can appear along the line. The theory applies to transmission lines of all frequencies including high-frequency transmission lines (such as telegraph wires and radio frequency conductors), audio frequency (such as telephone lines), low frequency (such as power lines) and direct current.

Distributed components[edit]

Schematic representation of the elementary components of a transmission line.

The telegrapher's equations, like all other equations describing electrical phenomena, result from Maxwell's equations. In a more practical approach, one assumes that the conductors are composed of an infinite series of two-port elementary components, each representing an infinitesimally short segment of the transmission line:

  • The distributed resistance R of the conductors is represented by a series resistor (expressed in ohms per unit length).
  • The distributed inductance L (due to the magnetic field around the wires, self-inductance, etc.) is represented by a series inductor (henries per unit length).
  • The capacitance C between the two conductors is represented by a shunt capacitor C (farads per unit length).
  • The conductance G of the dielectric material separating the two conductors is represented by a shunt resistor between the signal wire and the return wire (siemens per unit length). This resistor in the model has a resistance of 1/G ohms.

The model consists of an infinite series of the infinitesimal elements shown in the figure, and that the values of the components are specified per unit length so the picture of the component can be misleading. An alternative notation is to use R', L', C ' and G ' to emphasize that the values are derivatives with respect to length. These quantities can also be known as the primary line constants to distinguish from the secondary line constants derived from them, these being the characteristic impedance, the propagation constant, attenuation constant and phase constant. All these constants are constant with respect to time, voltage and current. They may be non-constant functions of frequency.

Role of different components[edit]

Schematic showing how a wave flows down a lossless transmission line terminated at an impedance-matched load resistor. Colors represent voltages; black dots represent electrons.

The role of the different components can be visualized based on the animation at right.

  • The inductance L makes it look like the electrons have inertia, i.e. with a large inductance, it is difficult to increase or decrease the current flow at any given point. Large inductance makes the wave move more slowly, just as waves travel more slowly down a heavy rope than a light one. It also gives it a higher impedance (lower current for the same voltage).
  • The capacitance C controls how much the bunched-up electrons repel each other, and conversely how much the spread-out electrons attract each other. With a large capacitance, there is less attraction and repulsion, because the other line (which always has the opposite charge) partly cancels out the attractive or repulsive force. (In other words, with large capacitance, the same amount of charge build-up creates less voltage). Large capacitance (weak restoring force) makes the wave move more slowly, and also gives it a lower impedance (lower voltage for the same current).
  • R corresponds to resistance within each line, and G allows electrons to jump from one line to the other. The figure at right shows a lossless transmission line, where both R and G are 0.

Values of primary parameters for telephone cable[edit]

Representative parameter data for 24 gauge telephone polyethylene insulated cable (PIC) at 70°F

Frequency R L G C
Hz Ω/km Ω/kft mH/km mH/kft µS/km µS/kft nF/km nF/kft
1 172.24 52.50 0.6129 0.1868 0.000 0.000 51.57 15.72
1k 172.28 52.51 0.6125 0.1867 0.072 0.022 51.57 15.72
10k 172.70 52.64 0.6099 0.1859 0.531 0.162 51.57 15.72
100k 191.63 58.41 0.5807 0.1770 3.327 1.197 51.57 15.72
1M 463.59 141.30 0.5062 0.1543 29.111 8.873 51.57 15.72
2M 643.14 196.03 0.4862 0.1482 53.205 16.217 51.57 15.72
5M 999.41 304.62 0.4675 0.1425 118.074 35.989 51.57 15.72

More extensive tables and tables for other gauges, temperatures and types are available in Reeve.[1] Chen[2] gives the same data in a parameterized form that he states is usable up to 50 MHz.

The variation of R and L is mainly due to skin effect and proximity effect.

The constancy of the capacitance is a consequence of intentional design.

The variation of G can be inferred from Terman[3] "The power factor ... tends to be independent of frequency, since the fraction of energy lost during each cycle ... is substantially independent of the number of cycles per second, over wide frequency ranges." A function of the form G(f) = G_1 \left( \frac {f}{f_1}\right)^{ge} with ge close to 1.0 would fit the statement from Terman. Chen [2] gives an equation of similar form.

G in this table can be modeled well with

f_1 = 1\;\mathrm{MHz}
G_1 = 29.11\;\mathrm{\mu S/km} = 8.873\;\mathrm{\mu S/kft}
ge = 0.87

Usually the resistive losses grow proportionately to  f^{0.5} \, and dielectric losses grow proportionately to  f^{ge} \, with ge > 0.5 so at a high enough frequency, dielectric losses will exceed resistive losses. In practice, before that point is reached, a transmission line with a better dielectric is used. The dielectric can be reduced down to air with an occasional plastic spacer.


Lossless transmission[edit]

When the elements R and G are very small, their effects can be neglected, and the transmission line is considered as an ideal lossless structure. In this case, the model depends only on the L and C elements. The Telegrapher's Equations then describe the relationship between the voltage V and the current I along the transmission line, each of which is a function of position x and time t:

 V = V(x,t)
 I = I(x,t)

The equations[edit]

The equations themselves consist of a pair of coupled, first-order, partial differential equations. The first equation shows that the induced voltage is related to the time rate-of-change of the current through the cable inductance, while the second shows, similarly, that the current drawn by the cable capacitance is related to the time rate-of-change of the voltage.


\frac{\partial V}{\partial x}  =
-L \frac{\partial I}{\partial t}

\frac{\partial I}{\partial x}  =
-C \frac{\partial V}{\partial t}


The Telegrapher's Equations are developed in similar forms in the following references: Kraus,[4] Hayt,[5] Marshall,[6] Sadiku,[7] Harrington,[8] Karakash,[9] Metzger,[10]

These equations may be combined to form two exact wave equations, one for voltage V, the other for current I:


\frac{\partial^2 V}{{\partial t}^2}  -
u^2 \frac{\partial^2 V}{{\partial x}^2}  = 0

\frac{\partial^2 I}{{\partial t}^2} -
u^2 \frac{\partial^2 I}{{\partial x}^2}  = 0


where

u = \frac{1}{\sqrt{LC}}

is the propagation speed of waves traveling through the transmission line.

Sinusoidal steady-state[edit]

In the case of sinusoidal steady-state, the voltage and current take the form of single-tone sine waves:

 V(x,t) = \mathrm{Re} \{ V(x) \cdot e^{ j\omega t  } \}
 I(x,t) = \mathrm{Re} \{ I(x) \cdot e^{ j\omega t  } \} ,

where \omega is the angular frequency of the steady-state wave. In this case, the Telegrapher's equations reduce to


\frac{d V}{d x}   =   -j \omega L I

\frac{ d I}{d x}   =    -j \omega C V

Likewise, the wave equations reduce to

\frac{d^2 V}{d x^2}+ k^2  V = 0
\frac{d^2 I}{d x^2} + k^2 I= 0

where k is the wave number:


k = \omega \sqrt{LC} =  {  \omega \over u } .

Each of these two equations is in the form of the one-dimensional Helmholtz equation.

For all transmission lines made of parallel perfect conductors with vacuum between them, this speed is equal to the speed of light.

In this case, it is possible to show that

V(x) = V_1 e^{-jkx} + V_2 e^{+jkx}

and

I(x) = { V_1 \over Z_0 } e^{-jkx} - { V_2 \over Z_0 }e^{+jkx}

where Z_0 is the characteristic impedance of the transmission line, which, for a lossless line is given by

Z_0 =  \sqrt { {L \over C}}

and V_1 and V_2 are arbitrary constants of integration, which are determined by the two boundary conditions (one for each end of the transmission line).

This impedance does not change along the length of the line since L and C are constant at any point on the line, provided that the cross-sectional geometry of the line remains constant.

The lossless line and distortionless line are discussed in Sadiku,[11] and Marshall,[12]

General solution[edit]

The general solution of the wave equation for the voltage is the sum of a forward traveling wave and a backward traveling wave:

V(x,t) \ = \ f_1(x - ut) + f_2(x + ut)

where

f1 represents a wave traveling from left to right in a positive x direction whilst f2 represents a wave traveling from right to left. It can be seen that the instantaneous voltage at any point x on the line is the sum of the voltages due to both waves.

Since the current I is related to the voltage V by the telegrapher's equations, we can write

I(x,t) \ = \ \frac{f_1(x - ut)}{Z_0} - \frac{f_2(x + ut)}{Z_0}

Lossy transmission line[edit]

When the loss elements R and G are not negligible, the original differential equations describing the elementary segment of line become


\frac{\partial}{\partial x} V(x,t) =
-L \frac{\partial}{\partial t} I(x,t) - R I(x,t)

\frac{\partial}{\partial x} I(x,t) =
-C \frac{\partial}{\partial t} V(x,t) - G V(x,t)

By differentiating the first equation with respect to x and the second with respect to t, and some algebraic manipulation, we obtain a pair of hyperbolic partial differential equations each involving only one unknown:


\frac{\partial^2}{{\partial x}^2} V =
L C \frac{\partial^2}{{\partial t}^2} V +
(R C + G L) \frac{\partial}{\partial t} V + G R V

\frac{\partial^2}{{\partial x}^2} I =
L C \frac{\partial^2}{{\partial t}^2} I +
(R C + G L) \frac{\partial}{\partial t} I + G R I

Note that these equations resemble the homogeneous wave equation with extra terms in V and I and their first derivatives. These extra terms cause the signal to decay and spread out with time and distance. If the transmission line is only slightly lossy (small R and G = 0), signal strength will decay over distance as ex, where α = R/2Z0

Signal pattern examples[edit]

Changes of the signal level distribution along the single dimensional transmission media. Depending on the parameters of the telegraph equation, this equation can reproduce all four patterns.

Depending on the parameters of the telegraph equation, the changes of the signal level distribution along the length of the single-dimensional transmission media may take the shape of the simple wave, wave with decrement, or the diffusion-like pattern of the telegraph equation. The shape of the diffusion-like pattern is caused by the effect of the shunt capacity.

Solutions of the telegrapher's equations as circuit components[edit]

Equivalent circuit of a transmission line described by the Telegrapher's equations.

The solutions of the telegrapher's equations can be inserted into a circuit as components of an equivalent sub-circuit as shown the figure. As drawn, all voltages are with respect to ground and all amplifiers have unshown connections to ground. An example of a transmission line modeled by this circuit would be an unbalanced transmission line such as a strip line on a circuit board. The impedance Z(s), the voltage doubler (the triangle with the number "2") and the difference amplifier (the triangle with the number "1") account for the interaction of the transmission line with the rest of the circuit. The T(s) blocks account for delay, attenuation, dispersion and whatever happens to the signal in transit. One of the T(s) blocks carries the "forward wave" and the other carries the "backward wave". The circuit, as depicted, is fully symmetric, although it is not drawn that way. The circuit depicted is equivalent to a transmission line connected from V1 to V2 in the sense that V1, V2, I1 and I2 would be same whether this circuit or an actual transmission line was connected between V1 and V2. There is no implication that there are actually amplifiers inside the transmission line.

This is not the only possible equivalent circuit. Voltage amplifiers and sensors can be replaced with current, transimpedance or transconductance amplifiers. Series impedances can be replaced with shunt admittances. The circuit can be augmented to account for different "grounds" at each end. The circuit can be made fully differential.

External links[edit]

See also[edit]

Notes[edit]

  1. ^ Reeve (1995, p. 558)
  2. ^ a b Chen (2004, p. 26)
  3. ^ Terman (1943, p. 112)
  4. ^ Kraus (1989, pp. 380–419)
  5. ^ Hayt (1989, pp. 382–392)
  6. ^ Marshall (1987, pp. 359–378)
  7. ^ Sadiku (1989, pp. 497–505)
  8. ^ Harrington (1961, pp. 61–65)
  9. ^ Karakash (1950, pp. 5–14)
  10. ^ Metzger (1969, pp. 1–10)
  11. ^ Sadiku (1989, pp. 501–503)
  12. ^ Marshall (1987, pp. 369–372)

References[edit]

  • Chen, Walter Y. (2004), Home Networking Basics, Prentice Hall, ISBN 0-13-016511-5 
  • Harrington, Roger F. (1961), Time-Harmonic Electromagnetic Fields, McGraw-Hill 
  • Hayt, William (1989), Engineering Electromagnetics (5th ed.), McGraw-Hill, ISBN 0-07-027406-1 
  • Karakash, John J. (1950), Transmission Lines and Filter Networks (1st ed.), Macmillan 
  • Kraus, John D. (1984), Electromagnetics (3rd ed.), McGraw-Hill, ISBN 0-07-035423-5 
  • Marshall, Stanley V. (1987), Electromagnetic Concepts & Applications (1st ed.), Prentice-Hall, ISBN 0-13-249004-8 
  • Metzger, Georges; Vabre, Jean-Paul (1969), Transmission Lines with Pulse Excitation, Academic Press 
  • Reeve, Whitman D. (1995), Subscriber Loop Signaling and Transmission Handbook, IEEE Press, ISBN 0-7803-0440-3 
  • Sadiku, Matthew N. O. (1989), Elements of Electromagnetics (1st ed.), Saunders College Publishing, ISBN 0030134846 
  • Terman, Frederick Emmons (1943), Radio Engineers' Handbook (1st ed.), McGraw-Hill