Wien bridge oscillator

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In this version of the oscillator, Rb is a small incandescent lamp. Usually R1 = R2 = R and C1 = C2 = C. In normal operation, Rb self heats to the point where its resistance is Rf/2.

A Wien bridge oscillator is a type of electronic oscillator that generates sine waves. It can generate a large range of frequencies. The oscillator is based on a bridge circuit originally developed by Max Wien in 1891 for the measurement of impedances.[1] The bridge comprises four resistors and two capacitors. The oscillator can also be viewed as a positive gain amplifier combined with a bandpass filter that provides positive feedback. Automatic gain control, intentional non-linearity and incidental non-linearity limit the output amplitude in various implementations of the oscillator.

The circuit shown to the right depicts a common implementation of the oscillator, with automatic gain control, using modern components. Under the condition that R1=R2=R and C1=C2=C, the frequency of oscillation is given by:

f=\frac{1}{2 \pi R C}

and the condition of stable oscillation is given by

R_b =  \frac {R_f} {2}


There were several efforts to improve oscillators in the 1930s. Linearity was recognized as important. The "resistance-stabilized oscillator" had an adjustable feedback resistor; that resistor would be set so the oscillator just started (thus setting the loop gain to just over unity). The oscillations would build until the vacuum tube's grid would start conducting current, which would increase losses and limit the output amplitude.[2][3][4] Automatic amplitude control was investigated.[5][6] Terman states, "The frequency stability and wave-shape form of any common oscillator can be improved by using an automatic-amplitude-control arrangement to maintain the amplitude of oscillations constant under all conditions."[7]

In 1937, Meacham described using a filament lamp for automatic gain control in bridge oscillators.[8][9]

Also in 1937, Scott described audio oscillators based on various bridges including the Wien bridge.[10][11]

Terman at Stanford University was interested in Black's work on negative feedback,[12][13] so he held a graduate seminar on negative feedback.[14] William Hewlett attended the seminar. Scott's February 1938 oscillator paper came out during the seminar. Here is a recollection by Terman:[15]

Fred Terman explains: "To complete the requirements for an Engineer’s degree at Stanford, Bill had to prepare a thesis. At that time I had decided to devote an entire quarter of my graduate seminar to the subject of 'negative feedback' I had become interested in this then new technique because it seemed to have great potential for doing many useful things. I would report on some applications I had thought up on negative feedback, and the boys would read recent articles and report to each other on current developments. This seminar was just well started when a paper came out that looked interesting to me. It was by a man from General Radio and dealt with a fixed-frequency audio oscillator in which the frequency was controlled by a resistance-capacitance network, and was changed by means of push-buttons. Oscillations were obtained by an ingenious application of negative feedback."

In June 1938, Terman, Buss, Hewlett and Cahill gave a presentation about negative feedback at the IRE Convention in New York; in August 1938, there was a second presentation at the IRE Pacific Coast Convention in Portland, OR; the presentation became an IRE paper.[16] One topic was amplitude control in a Wien bridge oscillator. The oscillator was demonstrated in Portland.[17] Hewlett, along with David Packard, co-founded Hewlett-Packard, and Hewlett-Packard's first product was the HP200A, a precision Wien bridge oscillator. The first sale was in January 1939.[18]

Hewlett's June 1939 engineer's degree thesis used a lamp to control the amplitude of a Wien bridge oscillator.[19] Hewlett's oscillator produced a sinusoidal output with a stable amplitude and low distortion.[20][21]

Oscillators without automatic gain control[edit]

Schematic of a Wien bridge oscillator that uses diodes to control amplitude. This circuit typically produces total harmonic distortion in the range of 1-5% depending on how carefully it is trimmed.

The conventional oscillator circuit is designed so that it will start oscillating ("start up") and that its amplitude will be controlled.

The oscillator at the right uses diodes to add a controlled compression to the amplifier output. It can produce total harmonic distortion in the range of 1-5%, depending on how carefully it is trimmed.[22]

For a linear circuit to oscillate, it must meet the Barkhausen conditions: its loop gain must be one and the phase around the loop must be an integer multiple of 360 degrees. The linear oscillator theory doesn't address how the oscillator starts up or how the amplitude is determined. The linear oscillator can support any amplitude.

In practice, the loop gain is initially larger than unity. Random noise is present in all circuits, and some of that noise will be near the desired frequency. A loop gain greater than one allows the amplitude of frequency to increase exponentially each time around the loop. With a loop gain greater than one, the oscillator will start.

Ideally, the loop gain needs to be just a little bigger than one, but in practice, it is often significantly greater than one. A larger loop gain makes the oscillator start quickly. A large loop gain also compensates for gain variations with temperature and the desired frequency of a tunable oscillator. For the oscillator to start, the loop gain must be greater than one under all possible conditions.

A loop gain greater than one has a down side. In theory, the oscillator amplitude will increase without limit. In practice, the amplitude will increase until the output runs into some limiting factor such as the power supply voltage (the amplifier output runs into the supply rails) or the amplifier output current limits. The limiting reduces the effective gain of the amplifier (the effect is called gain compression). In a stable oscillator, the average loop gain will be one.

Although the limiting action stabilizes the output voltage, it has two significant effects: it introduces harmonic distortion and it affects the frequency stability of the oscillator.

The amount of distortion is related to the extra loop gain used for startup. If there's a lot of extra loop gain at small amplitudes, then the gain must decrease more at higher instantaneous amplitudes. That means more distortion.

The amount of distortion is also related to final amplitude of the oscillation. Although an amplifier's gain is ideally linear, in practice it is nonlinear. The nonlinear transfer function can be expressed as a Taylor series. For small amplitudes, the higher order terms have little effect. For larger amplitudes, the nonlinearity is pronounced. Consequently, for low distortion, the oscillator's output amplitude should be a small fraction of the amplifier's dynamic range.

Meacham's bridge stabilized oscillator[edit]

Simplified schematic of a Meacham's bridge oscillator published in Bell System Technical Journal, Oct 1938. Unmarked capacitors have enough capacitance to be considered short circuits at signal frequency. Unmarked resistors and inductor are considered to be appropriate values for biasing and loading the vacuum tube. Node labels in this figure are not present in the publication.

Meacham disclosed the bridge oscillator circuit shown to the right in 1938. The circuit was described as having very high frequency stability and very pure sinusoidal output.[9] Instead of using tube overloading to control the amplitude, Meacham proposed a circuit that set the loop gain to unity while the amplifier is in its linear region. Meacham's circuit included a quartz crystal oscillator and a lamp in a Wheatstone bridge.

In Meacham's circuit, the frequency determining components are in the negative feed back branch of the bridge and the gain controlling elements are in the positive feed back branch. The crystal, Z4, operates in series resonance. As such it minimizes the negative feedback at resonance. The particular crystal exhibited a real resistance of 114 ohms at resonance. At frequencies below resonance, the crystal is capacitive and the gain of the negative feedback branch has a negative phase shift. At frequencies above resonance, the crystal is inductive and the gain of the negative feedback branch has a positive phase shift. The phase shift goes through zero at the resonant frequency. As the lamp heats up, it decreases the positive feedback. The Q of the crystal in Meacham's circuit is given as 104,000. At any frequency different from the resonant frequency by more than a small multiple of the bandwidth of the crystal, the negative feedback branch dominates the loop gain and there can be no self-sustaining oscillation except within the narrow bandwidth of the crystal.

Hewlett's oscillator[edit]

Simplified schematic of a Wien bridge oscillator from Hewlett’s US patent 2,268,873. Unmarked capacitors have enough capacitance to be considered short circuits at signal frequency. Unmarked resistors are considered to be appropriate values for biasing and loading the vacuum tubes. Node labels and reference designators in this figure are not the same as used in the patent. The vacuum tubes indicated in Hewlett's patent were pentodes rather than the triodes shown here.

Hewlett's Wien bridge oscillator can be considered as a combination of a differential amplifier and a Wien bridge, connected in a positive feedback loop between the amplifier output and differential inputs. At the oscillating frequency, the bridge is almost balanced and has very small transfer ratio. The loop gain is a product of the very high amplifier gain and the very low bridge ratio.[23] In Hewlett's circuit, the amplifier is implemented by two vacuum tubes. The amplifier's inverting input is the cathode of tube V1 and the non-inverting input is the control grid of tube V2. To simplify analysis, all the components other than R1, R2, C1 and C2 can be modeled as a non-inverting amplifier with a gain of 1+Rf/Rb and with a high input impedance. R1, R2, C1 and C2 form a bandpass filter which is connected to provide positive feedback at the frequency of oscillation. Rb self heats and increases the negative feedback which reduces the amplifier gain until the point is reached that there is just enough gain to sustain sinusoidal oscillation without over driving the amplifier. If R1 = R2 and C1 = C2 then at equilibrium Rf/Rb = 2 and the amplifier gain is 3. When the circuit is first energized, the lamp is cold and the gain of the circuit is greater than 3 which ensures start up. The dc bias current of vacuum tube V1 also flows through the lamp. This does not change the principles of the circuit's operation, but it does reduce the amplitude of the output at equilibrium because the bias current provides part of the heating of the lamp.

Hewlett's thesis made the following conclusions:[24]

A resistance-capacity oscillator of the type just described should be well suited for laboratory service. It has the ease of handling of a beat-frequency oscillator and yet few of its disadvantages. In the first place the frequency stability at low frequencies is much better than is possible with the beat-frequency type. There need be no critical placements of parts to insure small temperature changes, nor carefully designed detector circuits to prevent interlocking of oscillators. As a result of this, the overall weight of the oscillator may be kept at a minimum. An oscillator of this type, including a 1 watt amplifier and power supply, weighed only 18 pounds, in contrast to 93 pounds for the General Radio beat-frequency oscillator of comparable performance. The distortion and constancy of output compare favorably with the best beat-frequency oscillators now available. Lastly, an oscillator of this type can be laid out and constructed on the same basis as a commercial broadcast receiver, but with fewer adjustments to make. It thus combines quality of performance with cheapness of cost to give an ideal laboratory oscillator.

Wien bridge[edit]

Main article: Wien bridge

Bridge circuits were a common way of measuring component values by comparing them to known values. Often an unknown component would be put in one arm of a bridge, and then the bridge would be nulled by adjusting the other arms or changing the frequency of the voltage source (see, for example, the Wheatstone bridge).

The Wien bridge is one of many common bridges.[25] Wien's bridge is used for precision measurement of capacitance in terms of resistance and frequency.[26] It was also used to measure audio frequencies.

The Wien bridge does not require equal values of R or C. The phase of the signal at Vp relative to the signal at Vout varies from almost 90° leading at low frequency to almost 90° lagging at high frequency. At some intermediate frequency, the phase shift will be zero. At that frequency the ratio of Z1 to Z2 will be purely real (zero imaginary part). If the ratio of Rb to Rf is adjusted to the same ratio, then the bridge is balanced and the circuit can sustain oscillation. The circuit will oscillate even if Rb / Rf has a small phase shift and even if the inverting and non-inverting inputs of the amplifier have different phase shifts. There will always be a frequency at which the total phase shift of each branch of the bridge will be equal. If Rb / Rf has no phase shift and the phase shifts of the amplifiers inputs are zero then the bridge is balanced when:[27]

\omega^2 = {1 \over R_1 R_2 C_1 C_2} and  {R_f \over R_b} = {C_1 \over C_2} + {R_2 \over R_1}

where ω is the radian frequency.

If one chooses R1 = R2 and C1 = C2 then Rf = 2 Rb.

In practice, the values of R and C will never be exactly equal, but the equations above show that for fixed values in the Z1 and Z2 impedances, the bridge will balance at some ω and some ratio of Rb/Rf.


Analyzed from loop gain[edit]

According to Schilling,[23] the loop gain of the Wien bridge oscillator, under the condition that R1=R2=R and C1=C2=C, is given by

T = \left( \frac { R C s  } {R^2 C^2 s^2 + 3RCs +1 } - \frac {R_b} {R_b + R_f } \right) A_0  \,

where  A_0   \, is the frequency-dependent gain of the op-amp (note, the component names in Schilling have been replaced with the component names in the first figure).

Schilling further says that the condition of oscillation is T=1 which, is satisfied by

  \omega = \frac {1} {R C} \rightarrow f = \frac {1} {2 \pi R C}\,


  \frac {R_f} {R_b}  =   \frac  {2 A_0 + 3} {A_0 - 3} \, with \lim_{A_0\rightarrow \infin} \frac {R_f} {R_b} = 2 \,

Another analysis, with particular reference to frequency stability and selectivity, is in Strauss (1970, p. 671) and Hamilton (2003, p. 449).

Frequency determining network[citation needed][edit]

 H(s) = \frac { R_1 / (1 + sC_1 R_1)  } {R_1 / (1 + sC_1 R_1) + R_2 + 1/(sC_2)}
 H(s) = \frac { s C_2 R_1 } {(1 + s C_1 R_1) (s C_2 R_1  / (1 + sC_1 R_1) + s C_2 R_2 + 1 )}
 H(s) = \frac { s C_2 R_1 } {s C_2 R_1 + (1 + s C_1 R_1) (s C_2 R_2 + 1 )}
 H(s) = \frac { s C_2 R_1 } {C_1 C_2 R_1 R_2 s^2 + (C_2 R_1 + C_2 R_2 + C_1 R_1) s + 1 }

Let R=R1=R2 and C=C1=C2

 H(s) = \frac { s C R } {C^2 R^2 s^2 + 3 C R s + 1 }

Normalize to CR=1.

 H(s) = \frac { s } {s^2 + 3 s + 1 }

Thus the frequency determining network has a zero at 0 and poles at −1.5±(√5/2) or −2.6180 and −0.38197. The resulting root locus traces the unit circle. When the gain is 1, the two real poles meet at −1 and split into a complex pair. At gain 3, the poles cross the imaginary axis. At gain 5, the poles meet on the real axis and split into two real poles.

Amplitude stabilization[edit]

The key to the Wien bridge oscillator's low distortion oscillation is an amplitude stabilization method that does not use clipping. The idea of using a lamp in a bridge configuration for amplitude stabilization was published by Meacham in 1938.[28] The amplitude of electronic oscillators tends to increase until clipping or other gain limitation is reached. This leads to high harmonic distortion, which is often undesirable.

Hewlett used an incandescent bulb as a power detector, low pass filter and gain control element in the oscillator feedback path to control the output amplitude. The resistance of the light bulb filament (see resistivity article) increases as its temperature increases. The temperature of the filament depends on the power dissipated in the filament and some other factors. If the oscillator's period (an inverse of its frequency) is significantly shorter than the thermal time constant of the filament, then the temperature of the filament will be substantially constant over a cycle. The filament resistance will then determine the amplitude of the output signal. If the amplitude increases, the filament heats up and its resistance increases. The circuit is designed so that a larger filament resistance reduces loop gain, which in turn will reduce the output amplitude. The result is a negative feedback system that stabilizes the output amplitude to a constant value. With this form of amplitude control, the oscillator operates as a near ideal linear system and provides a very low distortion output signal. Oscillators that use limiting for amplitude control often have significant harmonic distortion. At low frequencies, as the time period of the Wien bridge oscillator approaches the thermal time constant of the incandescent bulb, the circuit operation becomes more nonlinear, and the output distortion rises significantly.

Light bulbs have their disadvantages when used as gain control elements in Wien bridge oscillators, most notably a very high sensitivity to vibration due to the bulb's microphonic nature amplitude modulating the oscillator output, a limitation in high frequency response due to the inductive nature of the coiled filament, and current requirements that exceed the capability of many op-amps. Modern Wien bridge oscillators have used other nonlinear elements, such as diodes, thermistors, field effect transistors, or photocells for amplitude stabilization in place of light bulbs. Distortion as low as 0.0003% (3 ppm) can be achieved with modern components unavailable to Hewlett.[29]

Wien bridge oscillators that use thermistors exhibit extreme sensitivity to ambient temperature due to the low operating temperature of a thermistor compared to an incandescent lamp.[30]

Automatic gain control dynamics[edit]

Root locus plot of Wien bridge oscillator pole positions for R1 = R2 = 1 and C1 = C2 =1 versus K = (Rb + Rf)/Rb. The numerical values of K are shown in a purple font. The trajectory of the poles for K=3 is perpendicular to the imaginary (β) axis. For K >> 5, one pole approaches the origin and the other approaches K.[31]

Small perturbations in the value of Rb cause the dominant poles to move back and forth across the jω (imaginary) axis. If the poles move into the left half plane, the oscillation dies out exponentially to zero. If the poles move into the right half plane, the oscillation grows exponentially until something limits it. If the perturbation is very small, the magnitude of the equivalent Q is very large so that the amplitude changes slowly. If the perturbations are small and reverse after a short time, the envelope follows a ramp. The envelope is approximately the integral of the perturbation. The perturbation to envelope transfer function rolls off at 6 dB/octave and causes -90° of phase shift.

The light bulb has thermal inertia so that its power to resistance transfer function exhibits a single pole low pass filter. The envelope transfer function and the bulb transfer function are effectively in cascade, so that the control loop has effectively a low pass pole and a pole at zero and a net phase shift of almost -180°. This would cause poor transient response in the control loop due to low phase margin. The output might exhibit squegging. Bernard M. Oliver[32] showed that slight compression of the gain by the amplifier mitigates the envelope transfer function so that most oscillators show good transient response, except in the rare case where non-linearity in the vacuum tubes canceled each other producing an unusually linear amplifier.


  1. ^ Wien 1891
  2. ^ Terman 1933
  3. ^ Terman 1935, pp. 283–289
  4. ^ Terman 1937, pp. 371–372
  5. ^ Arguimbau 1933
  6. ^ Groszkowski 1934
  7. ^ Terman 1937, p. 370
  8. ^ Meacham 1939
  9. ^ a b Meacham 1938
  10. ^ Scott 1939
  11. ^ Scott 1938
  12. ^ Black 1934a
  13. ^ Black 1934b
  14. ^ HP 2002
  15. ^ Sharpe n.d.
  16. ^ Terman et al. 1939
  17. ^ Sharpe n.d., p. ???[page needed]; Packard remembers first demonstation of the 200A in Portland.
  18. ^ Sharpe n.d., p. xxx[page needed]
  19. ^ Williams (1991, p. 46) states, "Hewlett may have adapted this technique from Meacham, who published it in 1938 as a way to stabilize a quartz crystal oscillator. Meacham's paper, "The Bridge Stabilized Oscillator," is in reference number five in Hewlett's thesis."
  20. ^ Hewlett 1942
  21. ^ Williams 1991, pp. 46–47
  22. ^ Graeme, Jerald G.; Tobey, Gene E.; Huelsman, Lawrence P. (1971). Operational Amplifiers, Design and Applications (1st ed.). McGraw-Hill. pp. 383–385. ISBN 0-07-064917-0. 
  23. ^ a b Schilling & Belove 1968, pp. 612–614
  24. ^ Hewlett 1939, p. 13
  25. ^ Terman 1943, p. 904
  26. ^ Terman 1943, p. 904 citing Ferguson & Bartlett 1928
  27. ^ Terman 1943, p. 905
  28. ^ Meacham 1938. Meacham1938a. Meacham presented his work at the Thirteenth Annual Convention of the Institute of Radio Engineers, New York City, June 16, 1938 and published in Proc. I. R. E. October 1938. Hewlett's patent (filed July 11, 1939) does not mention Meacham.
  29. ^ Williams 1990, pp. 32–33
  30. ^ Strauss 1970, p. 710, stating "For acceptable amplitude stability, some form of temperature compensation would be necessary."
  31. ^ Strauss 1970, p. 667
  32. ^ Oliver 1960


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